Method for measuring microwave electromagnetic fields

ABSTRACT

A microwave signal is transmitted from a transmitting antenna through a transfer medium to an electrically modulated and mechanically spun microwave scatterer. The scatterer may include an electric field responsive antenna, such as a dipole, for measurement of the electric field, or a magnetic field responsive antenna, such as a loop, for measurement of the magnetic field. An impedance within the scatterer is electrically modulated at an audio frequency, and the scatterer is mechanically spun at an angular frequency substantially below that at which it is electrically modulated. The scatterer thereby re-radiates to a receiving antenna a signal at the microwave source frequency which is modulated at both the frequency of electrical modulation and the mechanical spinning frequency of the scatterer. Signals from the microwave source and from the receiving antenna are combined to yield an output signal having a magnitude which is a function of the magnitude of the field received by the scatterer and which is phase shifted proportional to the phase shift of the microwave signal from the transmitting antenna to the scatterer and thence to the receiving antenna. The output signal may be compared with a signal coherent with the frequency of rotation of the scatterer to determine the tilt angle of the electric or magnetic field received by the scatterer.

REFERENCE TO RELATED APPLICATION

This is a continuation of co-pending application Ser. No. 958,189, filedNov. 6, 1978 now U.S. Pat. No. 4,195,262.

BACKGROUND OF THE INVENTION

1. Field of the Invention

This invention pertains generally to the field of electromagnetic fieldmeasurements and more particularly to apparatus for measuringelectromagnetic fields using modulated scatterers.

2. Description of the Prior Art

Measurement of the characteristics of the radiated field from theantenna is of practical importance in antenna design, as well as forother purposes including the determination of the characteristics of themedium through which the radiated wave passes. Numerous techniques havebeen developed to obtain the desired radiated field measurements. See,e.g. W. H. Kummer, et al., "Antenna Measurements--1978," Proceedings ofthe IEEE, Vol. 66, No. 4, April, 1978. Using transform techniques andcomputers, it is possible to measure the near-field of an antennaaperture, and predict the far-field with substantial precision. Suchmeasurement techniques eliminate the need for large antenna testingranges or large anechoic chambers, and allow antennas in the field to betested quickly after installation.

A common current technique of measuring field distributions involves theuse of two mutually orthogonal polarized antennas. The output of eachantenna is alternatively switched and each is measured in time sequenceusing a single radio frequency receiver. Several problems areencountered when using this technique, including the difficulty ofcompletely uncoupling and balancing the two antennas. The radiofrequency signals received by the two antennas must be transmitted viawaveguides or coaxial cables to a synchronous switch connected to aradio frequency receiver. This additional equipment can affect the fieldbeing measured. Generally, the orthogonal antennas can only measure theorthogonal components of the electric field. While this may besufficient in some applications, if the tilt of the polarization ellipseand the ratio of the major axis to minor axis is desired, then the datamust be further processed by a computer.

Electric field distributions have been measured utilizing the backscattered signal from a modulated electric dipole or a spun dipole.However, previous techniques for making such field measurements have notbeen able to simultaneously determine, in real-time, the magnitude,phase shift, and polarization of the electric or magnetic field at thescatterer.

SUMMARY OF THE INVENTION

The apparatus in accordance with the invention includes a transmittingantenna which receives a microwave signal from a microwave source andtransmits it through a medium to a modulated scatterer. The scattererreceives the microwave signal and re-radiates a signal back to areceiving antenna, which in a monostatic system is the transmittingantenna. The scatterer may consist of an electric field responsiveantenna (e.g., a dipole) for measurement of the electric fieldcomponent, or a magnetic field responsive antenna (e.g., a loop) formeasurement of the magnetic field component. In either case, thescatterer includes a modulatable impedance which is modulated by anelectrical signal at a frequency substantially below the microwavesignal frequency. The scatterer is also mechanically spun about an axisat an angular frequency substantially lower than that at which itsimpedance is modulated. The signal that is radiated from the scattererthus will be modulated at the audio frequency at which its impedance ismodulated and at the frequency at which it is spun.

The signal that is received from the scatterer is combined with a signalfrom the microwave source and thereafter demodulated to yield an outputsignal which is at the frequency at which the scatterer impedance ismodulated, and which is phase shifted proportional to the phase shift ofthe microwave signal received by the receiving antenna. The outputsignal has a magnitude which is a function of the magnitude of eitherthe electric or magnetic field received by the scatterer and is furtherindependent of the phase shift of the received signal.

Means are also provided for comparing the phase of the output signalwith the phase of a signal which is coherent with the frequency of theelectrical signal modulating the scatterer impedance. By comparing thephase of the two signals, the phase shift of the microwave signal fromthe transmitting antenna to the scatterer and back to the receivingantenna can thereby be measured.

In addition, means are further provided for comparing the envelope ofthe output signal with a signal which is coherent with the frequency ofspinning of the scatterer, to allow measurement of the tilt angle of themajor axis of the electric or magnetic field received by the scatterer.The extent to which the major axis is tilted can be determined becausethe dipole or loop progressively passes into and out of alignment withthe major and minor axes of the field, resulting in a variation of themagnitude of the detected output signal as a function of angularposition of the scatterer. By comparing the angular position of thescatterer over time with the maximum or minimum of the envelope of thedetected output signal, it is possible to determine the direction ofpolarization relative to some arbitrary reference. It is also possibleto measure polarization properties by observing the change in phaseshift as a function of scatterer angular position over time.

The apparatus of the invention provides substantially continuous outputsignals indicative of the field characteristics. The output signalinformation may be read from an oscilloscope in real time by anoperator, or the information may be stored and placed in a form suitablefor further processing by computer. In either case, because theinformation on the field characteristics are compiled continuously, thescatterer can be quite readily moved about in space to measure the fieldcharacteristics at various positions. Complete measurement of the fieldradiated from an antenna thus can be obtained very quickly in comparisonwith present methods. The apparatus of the invention can also beutilized to obtain information about the characteristics of materialsthrough which the microwave signal passes, since the characteristics ofthe material may affect the attenuation of the microwave signal as wellas its phase shift and depolarization.

Further objects, features and advantages of the invention will beapparent from the following detailed description when taken inconjunction with the accompanying drawings.

BRIEF DESCRIPTION OF THE DRAWINGS

In the drawings:

FIG. 1 is a schematic view of monostatic measurement apparatus inaccordance with the inventin having a single antenna which transmits andreceives microwave radiation.

FIG. 2 is a schematic view of bistable measurement apparatus inaccordance with the invention wherein one antenna is provided fortransmitting a microwave signal and a second antenna is provided forreceiving a scattered microwave signal.

FIG. 3 is an illustrative pictorial representation of a typical shape ofthe electric field at the scatterer.

FIG. 4 is an illustrative pictorial representation of the magnitude ofthe detected output signal as a function of the angular position of thescatterer, which is proportional to the square of the magnitude of theelectric field at the scatterer.

FIG. 5 is a similar pictorial representation of the measured phase shiftof the microwave signal as a function of the angular position of thescatterer.

FIG. 6 is a somewhat simplified view of a dipole scatterer which isrotated by an electric motor and has slip rings for transmitting theelectrical modulation signal to the dipole.

FIG. 7 is a somewhat simplified view of another device for rotating adipole scatterer utilizing an electric motor and a radio frequencytransmitter for broadcasting the dipole modulating signal.

FIG. 8 is a somewhat simplified view of a loop scatterer device utilizedfor measuring the magnetic field components of microwave radiation.

FIG. 9 is another diopole scatterer in which the modulatable impedanceincludes a photocell which is provided with a source of chopped lightwhich impinges upon and modulates the photocell.

DESCRIPTION OF THE PREFERRED EMBODIMENTS

With reference to the drawings, wherein the numerals refer to like partsin each view, a monostatic apparatus for measuring microwaveelectromagnetic fields in accordance with the invention is showngenerally at 10 in FIG. 1. The apparatus includes a microwave signalsource 11 which transmits the microwave signal through a wave guide 12to a circulator 13. The signal is transmitted through the circulator inthis monostatic system through a wave guide portion 14, which includes atuner shown schematically at 15, to a transmitting antenna 16. Themicrowaves radiated from the antenna 16 pass through the transmissionmedium to a dipole scatterer 17 having a modulatable impedance 18connected in the middle of the dipole. In the following description, theinvention will be illustrated with reference to a dipole antenna formeasurement of the electric field component, and a loop for measurementof the magnetic field component. It is apparent that more complexantenna structures could be utilized which are selectively responsive toeither the electric or the magnetic field component of the radiatedwave.

An electrical signal from a signal source 20 at a frequency ω_(m) isprovided to the modulatable impedance 18 to vary its effective impedanceat the frequency ω_(m). The frequency of impedance modulation is chosento be substantially less than the microwave frequency to allow adequatemodulation, preferably being at least a ratio of 10 to 1 less than thefrequency of the microwave source. Generally, good results areobtainable when the frequency ω_(m) is in the high audible range, e.g.15 to 20 kHz. The scatterer 17 is also mechanically spun about an axisof rotation through its center at an angular frequency ω_(s) which issubstantially less than the frequency ω_(m) at which the dipoleimpedance is modulated, that is, at least by a factor of 10 to 1 less.

The dipole scatterer 17 receives energy from the electric field portionof the microwave signal and re-radiates a microwave signal at the samefrequency back to the transmitting antenna 16. However, the signal thatis radiated or "scattered" from the scatterer 17 is modulated first atthe frequency ω_(m) at which the internal impedance 18 of the dipole ismodulated, and secondly at twice the angular frequency ω_(s) at whichthe dipole is spun. Modulation at this second frequency occurs because,as the dipole rotates, it progressively passes into and out of alignmentwith the axis of polarization of the electric field. Unless the electicfield is perfectly circularly polarized, the magnitude of the electricfield seen by the dipole will pass from a maximum to a minimum and backto a maximum again twice during each rotation of the dipole.

The signal from the dipole 17 which is received by the antenna 16 istransmitted through the circulator 13 to a wave guide 22 and then isequally split for transmission to a first balanced mixer 23 and througha wave guide 24 to a second balanced mixer 25. The microwave signal fromthe source 11 is transmitted through a directional coupler 27 to a 3 dB90° hybrid junction 28. The junction 28 splits the reference signal andtransmits the reference signal phase shifted by 90° to the secondbalanced mixer and also transmits the reference signal without phaseshift through a wave guide 29 to the first balanced mixer 23. The outputof the second balanced mixer 25 is passed through a 90° phase shifter 30to an adder 31 wherein it is summed with the output signal of the firstbalanced mixer 23. The output of the adder is passed to a narrow bandamplifier 32 having a pass band centered at the dipole impedancemodulation frequency ω_(m) to filter out noise and extraneousinformation signals. Since the magnitude of the output of the adder willbe modulated at twice the frequency ω_(s) at which the dipole is spun,it is preferred that the band width of the amplifier be at least 4ω_(s).

The output of the narrow band amplifier 32 is directed to an envelopedetector 34 and a phase meter 35. The phase meter 35 also receives forcomparison the dipole impedance modulating signal at the frequency ω_(m)from the modulating signal source 20. The output of the envelopedetector may be connected to any suitable read-out device or to signalprocessing circuitry (not shown) for further operations on the data.Real-time monitoring of the output may be provided by connecting theoutput of the envelope detector to an oscilloscope 36. The wave formsseen on the oscilloscope, as explained below, will be a time varyingsignal whose maximums and minimums correspond to the alignment of thedipole with the major and minor axes respectively of the radiatedelectric field.

The output of the phase meter 35 is a time varying signal proportionalto the phase shift between the dipole impedance modulation referencesignal and the phase of the output signal from the narrow band amplifier32. The output of the narrowband amplifier will be at the same frequencyω_(m) as the modulation signal, but will be phase shifted proportionalto the phase shift of the microwave signal passing from the antenna tothe scatterer and back again. Real-time monitoring of the output of thephase meter may be obtained by providing the output signal to anoscilloscope 38 for viewing by the operator.

To obtain the depolarization of the wave from the antenna to thescatterer and back again, it is necessary to compare the output signalfrom either the envelope detector or the phase meter with a signal atthe frequency of rotation ω_(s) of the scatterer. This signal can beobtained in various ways, as explained below, and can be fed to theoscilloscopes 36 and 38 to allow triggering of the oscilloscopes atselected points on the wave form of the signal at the ω_(s) frequency.The scatterer rotation frequency signal may also be recorded in timesynchrony with the outputs of the envelope detector or of the phasemeter, and may be further processed by data processing equipment (notshown) using conventional programing techniques to yield a permanentread-out of data concerning the field at the various points at which thescatterer is positioned.

The operation of the apparatus of FIG. 1 is best explained withreference to the graphic diagrams of FIGS. 3-5. FIG. 3 is a typicalrepresentation of the locus of the instantaneous electric field at anangle θ and overlayed locus of the RMS field at the same angle, withthese shapes being chosen arbitrarily for illustrative purposes. FIG. 4is a graph of the output of the envelope detector as a function of θover time, and FIG. 5 is a similar graph of the phase shift φ over timeas a function of θ. These output signals are obtained using the phaseinsensitive coherent detector arrangement shown in FIG. 1. Thiscircuitry is also know as a single side-band suppressed carrierdemodulator, since it has the form of a single side-band suppressedcarrier quadrature type modulator. Such circuits have also been utilizedas image rejection mixers in superheterodyne systems.

To facilitate an understanding this system, it may be first assumed thatthe scatterer 18 is only electrically modulated at a frequency ω_(m) andis not spun. In this case, it can be shown that output signal e_(x) fromthe first balanced mixer 23 is of the form ##EQU1## and that the outputsignal e_(y) of the second balanced mixer 25 is of the form ##EQU2## Inthe foregoing expressions, A is the amplitude of the reference signalsat the microwave frquency fed through the junction 28 to the mixers, andb is the amplitude of the signal at the mixers received back from thescatterer through the antenna 16. It is assumed that A is much largerthan b, e.g., 30 dB or more. The amplitude factor (conversion gain) K₁ Ais used where the mixer is operating in its square law region for lowlevel signals, and the constant K_(h) is used for high level signalswhere the mixers are operating as linear rectifiers.

The output of the adder 31 will be proportional to the followingexpression: ##EQU3## where E is the vector electric field received bythe scatterer and u₁ is the unit vector along the scatterer. φ is thephase shift of the microwave signal from the antenna to the scatterer.Thus, when the output of the adder 31 has passed through the narrow bandamplifier 32, the output signal will be centered at a frequency ω_(m),will have a magnitude proportional to the square of the magnitude of theelectric field along the scatterer, and will be phase shifted by twicethe phase shift of the microwave signal from the antenna to thescatterer. If the scatterer is stationary, the output of the envelopedetector 34 will be a constant signal proportional to |E·u₁ |², and theoutput of the phase meter will be a constant signal proportional to 2φ.

It should be apparent to those skilled in the art that the relativephase shift between the two outputs of the 3 dB hybrid coupler 28 couldbe plus or minus 90°. Similarly, the phase shifter 30 could shift thesignal passing through it at frequency ω_(m) by plus or minus 90°, andthe adder 31 could equally serve to subtract its two inputs. In all ofthese several possibilities, the signal at the input of the narrowbandamplifier 32 is of the form ##EQU4## It is therefore seen that theessential features of the system are retained, regardless of whether thephase is shifted by plus or minus 90° in junction 28 or phase shifter30, whether they are associated with the first or second balancedmixers, or whether device 31 is an adder or subtractor.

Since the dipole scatterer 17 is in fact being spun at a frequencyω_(s), the magnitude of the output of the envelope detector will vary ata frequency of twice ω_(s). The output of the phase meter will also varyover time with a cycle repeating at a frequency of 2 ω_(s). Although thelocus of the instantaneous electric field is elliptical, as shown by theline labeled 40 in FIG. 3, it is actually the mean square of the fieldwhich is being measured, i.e. |E·u₁ |². The RMS electric field magnitudehas somewhat of a figure 8 pattern, as shown by the line 41 in FIG. 3,consisting of two intersecting circles in which the ellipse isinscribed. The field seen by the scatterer will be maximum when theangle of the dipole θ is equal to the tilt of the major axis of theelectric field at the angle Θ from the X axis, and a relatively sharpminimum in the RMS field will occur when the dipole angle aligns withthe minor axis of the electric field at the field angle Θ plus or minusπ/2. Either the maximum or the minimum of the means square field can beused to establish the tilt angle Θ, although it is apparent that sincethe minimum is relatively sharp, it is easier to use the minimum value.The ratio of E_(x) /E_(y) is the ratio of the field at the major axis tothe field at the minor axis of an elliptically polarized field.

A means for determining the tilt angle Θ of the major axis of thepolarization ellipse is obtained by comparison of the output signal witha signal at frequency ω_(s) from the device that mechanically spins thescatterer. The signal should be coherent with the frequency of rotationof the scatterer, that is, bear a fixed phase relationship. Where asynchronous motor is utilized, the line voltage signal can be brought tothe read-out oscilloscope 36 and compared in time synchrony with thesignal from the envelope detector 34, for example by using a dual traceoscilloscope or by using line voltage to trigger the oscilloscope.Alternatively, the signal at the dipole rotation frequency may bebrought to the phase reading oscilloscope 38 and compared with theoutput of the phase meter, which is shown illustratively in FIG. 5, todetermine the tilt angle Θ. In the graphical views of both FIGS. 4 and5, the angle θ of the dipole with respect to a chosen x axis is equal toω_(s) t, where t is time.

A bistatic apparatus for performing the electric field measurementsdescribed above is shown generally at 50 in FIG. 2. The bistaticapparatus 50 is substantially identical to the monostatic apparatus 10except that the microwave signal source 11 delivers the microwave signaldirectly through a wave guide 51 to a transmitting antenna 52, and themicrowave signal from the scatterer 17 is received by a separatereceiving antenna 54. The receiving antenna 54 is connected to a waveguide 55 which delivers the received signal to the balanced mixers 23and 25. In all other respects the circuit is identical to that shown inFIG. 1 and functions in the same manner.

A first scattering probe structure for providing a spinning dipole andthe required reference signals is shown generally at 60 in FIG. 6. Theprobe 60 includes dipole arms 61 composed of conductive metal leads anda diode rectifier 62 (preferably a microwave PIN diode) electricallyconnected between the two dipole arms. To provide modulation to thediode 62, electrically conductive wire leads 64 are connected to thedipole arms on either side of the diode and extend back a short distanceto slip rings 65. The slip rings are mounted around a central shaft 67to which the dipole is centrally mounted. The shaft 67, which ispreferably made of a microwave transparent material, extends back to asynchronous electric motor 68. The slip rings made contact with brushes69 connected by electrical leads 70 to the signal generator 20 whichprovides the modulating electrical signal at the frequency ω_(m). Powerlines 71 extend from the motor 68 to a source of AC power, with thepower line frequency then being utilized as the reference frequencyω_(s) for comparison purposes in the readout oscilloscopes 36 and 38.The leads 64 which extend from the slip rings 65 to the diode arepreferably fine magnet wire insulated with enamel. To avoid disturbingthe field, it is desirable that these leads be oriented normal to theelectric field. Alternatively, high resistance leads which areessentially transparent to radio frequency waves can be used. The motor65, its supports, and the shaft 67 are preferably covered with microwaveabsorber material (not shown) to reduce their influence on the field tothe maximum extent possible.

It is noted that the modulating oscillator which provides the modulatingfrequency ω_(m) can be designed and built as an integral part of theshaft 67. Slip rings may be utilized to provide the ω_(m) frequencyreference signal to the measurement circuitry. Alternatively, a radiofrequency transmitter can be utilized to transmit this signal. Anexample of such a scattering probe is shown in FIG. 7. This deviceinlcudes a dipole 75, a centrally connected diode 76 between the arms ofthe dipole, a shaft 77 to which the dipole is centrally mounted, and apair of electrical leads 78 connected on either side of the dioderunning back through the shaft to the ω_(m) frequency oscillator 79. Theoscillator 79 is mounted to the shaft and rotates with it. Likewisemounted on the shaft are a DC supply battery 80 and a radio frequencytransmitter 81 which transmits a high frequency radio signal modulatedat the modulating frequency ω_(m) to a remote receiver 83. The receiver83 detects the ω_(m) frequency signal and provides it through anisolation amplifier 84 to the phase meter 35. The shaft 77 is rotated byan electric motor 86 which is synchronously driven from AC electricpower lines 87.

Another means for modulating the impedance of the device is shown inFIG. 9, wherein a diode 90 has its conducting arms 91 electricallyconnected together by a diode 92. A photocell 93 is electricallyconnected around the diode 92 and receives on its face chopped lightfrom a source of high frequency chopped light 94. The light source 94provides light at a frequency ω_(m). The dipole is mounted to a shaft 95which is itself connected to a motor (not shown) for rotation.

It is apparent that a number of other techniques can be utilized tosupply the modulation reference frequency signal at frequency ω_(m) andthe dipole spinning frequency signal at frequency ω_(s). For example,the ω_(s) spinning frequency signal would be provided by mountingvarious devices such as tachometers or synchro transformers to theoutput shaft, or by using simple switch contacts or optical detectors onthe rotating shaft which provides an electrical signal each time thespinning dipole completes a revolution.

The foregoing diode scatterer is utilized to measure the electric fieldcomponent of microwave radiation. As indicated above, a more complexantenna can be used which responds to a single electric field component.In an entirely analogous manner, the magnetic field component of thewave can be measured utilizing an antenna selectively responsive to themagnetic field components such as the loop shown in FIG. 8 at 100. Theloop 100 contains at least one modulatable impedance therein such as thediode 101. For purposes of properly electrically balancing the loop, itis desired that a second diode 102 be placed in the opposite leg of theloop 100. Highly resistive electrical leads 103 are connected to theloop on either side of one of the diodes and extend back through arotating shaft 105 which is centrally mounted to one end of the loop.The electrical leads 103 provide an electrical signal which essentiallymodulates the impedance of the diode 101 at the modulating frequencyω_(m). The shaft is rotated at the spinning frequency ω_(s). The phaseinsensitive detection circuits of FIGS. 1 and 2 may be utilized todetect the signal that is scattered from the loop 100, and the outputsthat are obtained from the envelope detector 34 and phase meter 35 areentirely analogous to those described above for measurement of thefield. In particular, the relative magnitude of the magnetic field Halong its major and minor axes, the tilt of the polarization ellipse,and the relative phase shift of the field are detected in the samemanner as described above for the electric field. The various devicesdescribed above for obtaining the reference signals at frequency ω_(m)and frequency ω_(s) can also be utilized in entirely the same manner formeasurement of the magnetic field component by the loop 100.

The operation of the scatterers can be optimized using various knowntechniques for maximizing the scattering cross-section. For example, thedipole can be made resonant, as by making its electrical length nearlyequal to λ/2, where λ is the wave length of the ratio frequency fieldbeing measured. The result is a self-resonant scatterer. Othertechniques can be utilized, such as making the dipole arms in a zig-zagconfiguration fabricated on a printed circuit board, or the use ofhelical arms. Below about 5 giga-hertz, the scattering cross-section ofa short dipole can be made nearly as large as that of a self-resonantdipole by adding extra inductance to make it resonant. This can beeasily accomplished by adding a turn or two of wire or a ferrite bead toeach dipole arm. It is also possible to increase scatteringcross-sections using negative resistance type loads, such as by usingtransfer electron semiconductors, Gunn, IMPATT or tunnel diodes.

The measurement of the magnetic field is normally done with the looporiented such that its axis of rotation is normal to the magnetic field,and the diodes in the two sides of the loop are perpendicular to theelectric field. If electrical modulation of the diodes is to be done vialeads, the leads should also preferably be oriented perpendicular to theelectric field. In order to minimize the effect of the leads on theelectric field, highly resistive leads are preferred. The loop can bemade self-resonant by making its circumference slightly greater than λ,the wave length of the microwave signal. Smaller resonant loops can bebuilt by using several turns, or by adding capacitance. The loop canalso be loaded with negative resistance diodes to make it active.

It is understood that the invention is not confined to the particularconstruction or arrangement of parts herein illustrated and described,but embraces all such modified forms thereof as come within the scope ofthe following claims.

I claim:
 1. A method of measuring the microwave field radiated from anantenna, comprising the steps of:(a) radiating microwaves from atransmitting antenna; (b) spinning a scattering antenna in the radiatedfield from the transmitting antenna with the scattering antenna beingprovided with a modulatable impedance electrically connected therein andbeing selectively responsive to the electric field component of theradiated microwave field; (c) simultaneously modulating the impedence inthe scattering antenna at a frequency substantially greater than theangular frequency at which the scattering antenna is spun; (d) receivingthe microwave radiation signal reradiated from the scattering antenna;(e) combining and demodulating the microwave signal from the scatteringantenna with a microwave signal being radiated from the transmittingantenna to yield an output signal at the frequency at which thescattering antenna impedance is modulated and phase shifted proportionalto the phase shift of the microwave signal received from the scatteringantenna, and with a magnitude which is independent of such phase shiftand a function of the magnitude of the electric field received by thescattering antenna; (f) comparing a signal at a frequency coherent withthe frequency of spinning of the scattering antenna with the outputsignal at the frequency at which the scattering antenna impedance ismodulated to allow the measurement of the relative tilt angle of themajor axis of the microwave electric field received by the scatteringantenna.
 2. A method of measuring the microwave field radiated from anantenna, comprising the steps of:(a) radiating microwaves from atransmitting antenna; (b) spinning a scattering antenna in the radiatedfield from the transmitting antenna with the scattering antenna beingprovided with a modulatable impedance electrically connected therein andbeing selectively responsive to the magnetic field component of theradiated microwave field; (c) simultaneously modulating the impedance inthe scattering antenna at a frequency substantially greater than theangular frequency at which the scattering antenna is spun; (d) receivingthe microwave radiation signal reradiated from the scattering antenna;(e) combining and demodulating the microwave signal from the scatteringantenna with a microwave signal being radiated from the transmittingantenna to yield an output signal at the frequency at which thescattering antenna impedance is modulated and phase shifted proportionalto the phase shift of the microwave signal received from the scatteringantenna, and with a magnitude which is independent of such phase shiftand a function of the magnitude of the magnetic field received by thescattering antenna; (f) comparing a signal at a frequency coherent withthe frequency of spinning of the scattering antenna with the outputsignal at the frequency at which the scattering antenna is modulated toallow measurement of the relative tilt angle of the major axis of themicrowave magnetic field received by the scattering antenna.
 3. A methodof measuring the effect of materials on the microwave field radiatedfrom an antenna, comprising the steps of:(a) radiating microwaves from atransmitting antenna; (b) spinning a scattering antenna in the radiatedfield from the transmitting antenna with the scattering antenna beingprovided with a modulatable impedance electrically connected therein andbeing selectively responsive to the electric field component of theradiated microwave field; (c) simultaneously modulating the impedence inthe scattering antenna at a frequency substantially greater than theangular frequency at which the scattering antenna is spun; (d) receivingthe microwave radiation signal reradiated from the scattering antenna;(e) combining and demodulating the microwave signal from the scatteringantenna with a microwave signal being radiated from the transmittingantenna to yield an output signal at the frequency at which thescattering antenna impendance is modulated and phase shiftedproportional to the phase shift of the microwave signal received fromthe scattering antenna, and with a magnitude which is independent ofsuch phase shift and a function of the magnitude of the electric fieldreceived by the scattering antenna; (f) comparing a signal at afrequency coherent with the frequency of spinning of the scatteringantenna with the output signal at the frequency at which the scatteringantenna impedance is modulated to allow measurement of the relative tiltangle of the major axis of the microwave electric field received by thescattering antenna, and (g) inserting a material to be tested in themicrowave field radiated from the transmitting antenna and repeatingsteps (b) through (f) to thereby allow the effect of the tested materialon the microwave field to be determined.
 4. A method of measuring theeffect of materials on the microwave field radiated from an antenna,comprising the steps of:(a) radiating microwaves from a transmittingantenna; (b) spinning a scattering antenna in the radiated field fromthe transmitting antenna with the scattering antenna being provided witha modulatable impedance electrically connected therein and beingselectively responsive to the magnetic field component of the radiatedmicrowave field; (c) simultaneously modulating the impedance in thescattering antenna at a frequency substantially greater than the angularfrequency at which the scattering antenna is spun; (d) receiving themicrowave radiation signal reradiated from the scattering antenna; (e)combining and demodulating the microwave signal from the scatteringantenna with a microwave signal being radiated from the transmittingantenna to yield an output signal at the frequency at which thescattering antenna impedance is modulated and phase shifted proportionalto the phase shift of the microwave signal received from the scatteringantenna, and with a magnitude which is independent of such phase shiftand a function of the magnitude of the magnetic field received by thescattering antenna; (f) comparing a signal at a frequency coherent withthe frequency of spinning of the scattering antenna with the outputsignal at the frequency at which the scattering antenna is modulated toallow measuremnt of the relative tilt angle of the major axis of themicrowave magnetic field received by the scattering antenna; and (g)inserting a material to be tested in the microwave field radiated fromthe transmitting antenna and repeating steps (b) through (f) to therebyallow the effect of the tested material on the microwave field to bedetermind.
 5. The method of claim 1, 2, 3 or 4 further including thestep of:comparing the pahse of the output signal at the frequency atwhich the scattering antenna impedance is modulated with a signalcoherent with the frequency at which the scattering antenna impedance ismodulated to allow measurement of the phase shift of the microwavesignal from the transmitting antenna to the scattering antenna and backagain.
 6. The method of claim 1, 2, 3 or 4 further including the step ofdetecting the envelope of the output signal at the frequency at whichthe scattering antenna impedance is modulated to provide a signalproportion to the magnitude of the microwave field component received bythe scattering antenna.
 7. The method of claim 1 or 3 wherein thescattering antenna is an electric dipole.
 8. The method of claim 2 or 4wherein the scattering antenna is a loop of electrical conductor.
 9. Themethod of claim 1, 2, 3 or 4 wherein the step of comparing a signal at afrequency coherent with the frequency of spinning of the scatteringantenna to measure the relative tilt angle includes the steps of:(1)detecting the envelop of the magnitude of the output signal at thefrequency at which the scattering antenna impedance is modulated, (2)comparing the envelope of the magnitude of the output signal with thesignal at a frequency coherent with the frequency of spinning of thescattering antenna.
 10. The method of claim 1, 2, 3 or 4 wherein thestep of combining and demodulating the microwave signal from thescattering antenna with a microwave signal radiated from thetransmitting antenna includes the steps of:(1) mixing a microwave signalas radiated from the transmitting antenna with the microwave signalreceived from the scattering antenna to provide a first mixed outputsignal, (2) phase shifting a microwave signal as radiated from thetransmitting antenna by 90°, (3) mixing the microwave signal phaseshifted by 90° with a microwave signal received from the scatteringantenna to produce a second mixed output signal, (4) phase shifting by90° the second mixed output signal, (5) adding the first mixed outputsignal with the phase shifted second mixed output signal, (6) passingthe added output signals through a narrowband amplifier centered at theimpedance modulation frequency to amplify the added mixed output signal.